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EUA5202
2-W Stereo Audio Power Amplifier with Mute
DESCRIPTION
The EUA5202 is a stereo audio power amplifier that delivering 2W of continuous RMS power per channel into 3- loads. When driving 1W into 8- speakers, the EUA5202 has less than 0.04% THD+N across its specified frequency range. Included within this device is integrated de-pop circuitry that virtually eliminates transients that cause noise in the speakers. Amplifier gain is externally configured by means of two resistors per input channel and does not require external compensation for settings of 2 to 20 in BTL mode (1 to 10 in SE mode). An internal input MUX allows two sets of stereo inputs to the amplifier. In notebook applications, where internal speakers are driven as BTL and the line (often headphone drive) outputs are required to be SE, the EUA5202 automatically switches into SE mode when the SE/BTL inputs is activated. Consume only 7mA of supply current during normal operation, and the EUA5202 also features a shutdown function for power sensitive applications, holding the supply current at 1A.
FEATURES
Output Power at 3 Load - 2W/ch at VDD=5V - 800mW/ch at 3V Low Supply Current and Shutdown Current Integrated Depop Circuit Mute and Shutdown Control Function Thermal Shutdown Protection Stereo Input MUX Bridge-Tied Load (BTL) or Single-Ended (SE) Modes. TSSOP-24 with Thermal Pad
APPLICATIONS
Notebook Computers Multimedia Monitors Digital Radios and Portable TVs
Block Diagram
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Typical Application Circuit
Figure 1. EUA5202 Minimum Configuration Application Circuit
Figure 2. EUA5202 Full Configuration Application Circuit
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Pin Configurations
Package Pin Configurations
TSSOP-24 with Thermal Pad, exposure on the bottom of the package
Pin Description
PIN PIN I/O DESCRIPTION
HP/ LINE
LBYPASS LHPIN
LLINE IN LOUT+ LOUTGND/HS LVDD MUTE IN MUTE OUT NC RBYPASS RHPIN RLINEIN ROUT+ ROUTRVDD SE/BTL SHUTDOWN TJ
16 6 5
4 3 10 1,12,13, 24 7 11 9 17,23 19 20 21 22 15 18 14 8 2
I
I
I O O I I O
Input MUX control input, hold high to select LHP IN or RHP IN (5, 20), hold low to select LLINE IN or RLINE IN (4, 21) Tap to voltage divider for left channel internal mid-supply bias Left channel headphone input, selected when HP/LINE terminal (16) is held high Left channel line input, selected when HP/LINE terminal (16) is held low Left channel + output in BTL mode, + output in SE mode Left channel - output in BTL mode, high-impedance state in SE mode
Ground connection for circuitry, directly connected to thermal pad Supply voltage input for left channel and for primary bias circuits Mute all amplifiers, hold low for normal operation, hold high to mute Follows MUTE IN terminal (11), provides buffered output No internal connection Tap to voltage divider for right channel internal mid-supply bias Right channel headphone input, selected when HP/LINE terminal (16) is held high Right channel line input, selected when HP/LINE terminal (16) is held low Right channel + output in BTL mode, + output in SE mode Right channel - output in BTL mode, high-impedance state in SE mode Supply voltage input for high channel Hold low foe BTL mod, hold high for SE mode Places entire IC in shutdown mode when held high, IDD=5A Sources a current proportional to the junction temperature. This terminal should be left unconnected during normal operation.
I I O O I I I O
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Ordering Information
Order Number Package Type Marking Operating Temperature range
EUA5202QIR EUA5202QIT
TSSOP 24 TSSOP 24
xxxx EUA5202 xxxx EUA5202
-40C to 85C -40C to 85C
EUA5202
1/4
1/4
1/4
Packing R: Tape& Reel T: Tube Operating temperature range I: Industry Standard Package Type Q: TSSOP
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Absolute Maximum Ratings
Supply voltage , VDD------------------------------------------------------------------------------------------6V Input voltage, V1----------------------------------------------------------------------------0.3V to VDD+0.3V Continuous total power dissipation------------------------------------------------------------internally limited Operating free-air temperature range ,TA ------------------------------------------------------- -40C to 85C Operating junction temperature range, TJ ------------------------------------------------------- -40C to 150C Storage temperature range, Tstg ----------------------------------------------------------------65C to 150C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds-------------------------------------260C
Recommended Operating Conditions
MIN NOM MAX UNIT
Supply Voltage, VDD VDD = 5V, 250m W/Ch average power, VDD = 5V, 2 W/Ch average power, VDD = 5V VDD = 3.3V
3 4- stereo BTL drive, with proper PCB design -40 3- stereo BTL drive, with proper PCB design -40 and 300 CFM forced-air cooling 1.25 1.25
5
5.5 85
V
Operating free-air temperature, TA
C 85 4.5 2.7
Common mode input voltage, VICM
V
DC Electrical Characteristics, TA=25C Symbol Parameter
VDD=5V IDD Supply Current VDD=3.3V VOO IDD (Mute) IDD(SD) Output Offset Voltage (measured differentially) Supply Current in Mute Mode IDD in Shutdown
Conditions
Stereo BTL Stereo SE Stereo BTL Stereo SE
EUA5202 Unit Min. Typ Max.
7.1 3.9 5.7 3.1 5 1.55 1 5 11 6 9 5 25 mA mA mA mA mV mA A
VDD=5V, Gain=2 VDD=5V VDD=5V
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Typical Ac Operating Characteristics, VDD=5V, TA=25C, RL=3 Symbol
PO THD+N
Parameter
Output Power(each channel)*1 Total Harmonic Distortion Plus Noise Maximum Output Power Bandwidth Supply Ripple Rejection Ratio Mute Attenuation Channel-to- Channel Output Separation Line/HP Input Separation BTL Attenuation in SE Mode Input Impedance Signal-to-Noise Ratio Output Noise Voltage
Conditions
THD=0.2%, BTL, See Figure 3 THD=1%, BTL, See Figure 3 PO=2W, f=1KHz ,See Figure5 V1=1V, RL=10k, AV=1V/V
Typ.
2 2.2 200 100 >20 65 40 85 85 88 86
Unit
W m% m% KHz dB dB dB dB dB M dB V(rms)
BOM
AV=10V/V THD <1%, See Figure5 f=1KHz, See Figure37 f=20-20KHz, See Figure37 f=1KHz, See Figure 39
Z1 VN
PO=2W,BTL, 5V See Figure 35
2 101 22
*1: Output Power is measured at the output terminals of the IC at 1 KHz
Typical Ac Operating Characteristics, VDD=3.3V, TA=25C, RL=3 Symbol
PO THD+N
Parameter
Output Power(each channel)*1 Total Harmonic Distortion Plus Noise Maximum Output Power Bandwidth Supply Ripple Rejection Ratio Mute Attenuation Channel-to- Channel Output Separation Line/HP Input Separation BTL Attenuation in SE Mode Input Impedance Signal - to - Noise Ratio Output Noise Voltage
Conditions
THD=0.2%, BTL, See Figure 10 THD=1%, BTL, See Figure 10 PO=2W, f=1KHz ,See Figure11 V1=1V, RL=10k, AV =1V/V
Typ.
800 900 350 200 >20 60 40 85 80 88 86
Unit
W m% m% KHz dB dB dB dB dB M dB V(rms)
BOM
AV=10V/V THD <1%, See Figure11 f=1KHz, See Figure37 f=20-20KHz, See Figure37 f=1KHz, See Figure 40
Z1 VN
PO=700mW,BTL, 5V See Figure 36
2 96 22
*1: Output Power is measured at the output terminals of the IC at 1 KHz
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Typical Operating Characteristics (Table of Graphs)
No
1 2 3 4 5 6 7 8 9
Item
THD+N vs. Output Power THD+N vs. Frequency THD+N vs. Frequency THD+N vs. Output Power THD+N vs. Frequency THD+N vs. Output Power THD+N vs. Output Power THD+N vs. Output Power THD+N vs. Frequency
Conditions
VDD=5VA RL=3 & 8 ohmA BTLA f=1KHz VDD=5VA RL=4 ohmA BTLA Po=1.5W f=20 to 20KHzA Av= -2 & -10 & -20V/V VDD=5VA RL=3 & 4 ohmA BTLA Po=1.5W A f=20 to 20KHz VDD=5VA RL=3 ohmA BTLA f=20 & 1K & 20KHz VDD=5VA RL=8 ohmA BTLA f=20 to 20KHzA Av=-2V/V VDD=5VA RL=8 ohmA BTLA Po=1WA Av= -2 &-10 & -20V/VA f=20 to 20KHz VDD=5VA RL=8 ohmA BTLA f=20 & 1K & 20KHz VDD=3.3VA RL=3 & 8 ohmA BTLA f=1KHz VDD=3.3VA RL=4 ohmA BTLA Po=0.75WA Av= -2 &-10 &-20V/VA f=20 to 20KHz VDD=3.3VA RL=4 ohmA BTLA Av=-2V/VA Po=0.1 & 0.35 & 0.75W & 800mW(RL=3 ohm) VDD=3.3VA RL=3 ohmA BTLA Av=-2V/VA f=20 & 1K & 20KHz VDD=3.3VA RL=8 ohmA BTLA Po=0.4W A Av=-2 &-10 & -20V/V VDD=3.3VA RL=8 ohmA BTLA Av=-2V/V A Po=0.1 & 0.25 & 0.4W VDD=3.3VA RL=8 ohmA BTLA Av= -2V/VA f=20 & 1K &20KHz VDD=5VA RL=4 ohmA SEA Po=0.5WA Av= -1&-5&-10V/V VDD=5VA RL=4 ohmA SEA Av= -2V/VA Po=0.1 & 0.25 & 0.5W VDD=5VA RL=4 ohmA SEA Av= -2V/VA f=100 & 1K & 20KHz VDD=5VA RL=8 ohmA SEA Po=0.25WA Av= -1 &-5 &-10V/V VDD=5VA RL=8 ohmA SEA Av= -2V/VA Po=0.05 & 0.1 & 0.25W VDD=5VA RL=8 ohmA SEA Av= -2V/VA f=100 &1K & 20KHz VDD=5VA RL=32 ohmA SEA Po=0.075WA Av= -1 &-5 &-10V/V VDD=5VA RL=32 ohmA SEA Av= -1V/VA Po=25 & 50 & 75mW VDD=5VA RL=32 ohmA SEA Av= -1V/VA f=20 & 1K & 20KHz VDD=3.3VA RL=4 ohmA SEA Po=0.2WA Av= -1 &-5 &-10V/V VDD=3.3VA RL=4 ohmA SEA Av= -1V/VA Po=0.05 & 0.1 & 0.2W VDD=3.3VA RL=4 ohmA SEA Av= -2V/VA f=100 & 1K & 20KHz VDD=3.3VA RL=8 ohmA SEA Po=100mWA Av= -1 &-5 &-10V/V VDD=3.3VA RL=8 ohmA SEA Av= -1V/VA Po=25 & 50 &100mW VDD=3.3VA RL=8 ohmA SEA Av= -1V/VA f=100 & 1K & 20KHz VDD=3.3VA RL=32 ohmA SEA Po=30mWA Av= -1 &-5 &-10V/V VDD=3.3VA RL=32 ohmA SEA Av= -1V/VA Po=10 & 20 & 30mW VDD=3.3VA RL=32 ohmA SEA Av=-1V/VA f=20 & 1K & 20KHz
Figure Page
3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 32 33 34
9 9 9 9 9 9 10 10 10 10 10 10 11 11 11 11 11 11 12 12 12 12 12 12 13 13 13 13 13 13 14 14
10 THD+N vs. Frequency 11 THD+N vs. Output Power 12 THD+N vs. Frequency 13 THD+N vs. Frequency 14 THD+N vs. Output Power 15 THD+N vs. Frequency 16 THD+N vs. Frequency 17 THD+N vs. Output Power 18 THD+N vs. Frequency 19 THD+N vs. Frequency 20 THD+N vs. Output Power 21 THD+N vs. Frequency 22 THD+N vs. Frequency 23 THD+N vs. Output Power 24 THD+N vs. Frequency 25 THD+N vs. Frequency 26 THD+N vs. Output Power 27 THD+N vs. Frequency 28 THD+N vs. Frequency 29 THD+N vs. Output Power 30 THD+N vs. Frequency 31 THD+N vs. Frequency 32 THD+N vs. Output Power
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33 Output Noise Voltage vs. Frequency VDD=5VA BW=22Hz to 22kHzA RL=4 34 Output Noise Voltage vs. Frequency VDD=3.3VA BW=22Hz to 22kHzA RL=4 35 36 37 38 39 40 41 42 43 44 45 46 47 48 49 50 51 52 53 54 55
14 14 14 14 15 15 15 15 15 15 16 16 16 16 16 16 17 17 17 17 17
Supply Ripple Rejection Ratio vs. RL=4 ohmA CB=4.7uFA BTLA VDD=3.3 & 5V Frequency Supply Ripple Rejection Ratio vs. RL=4 ohmA CB=4.7uFA SEA VDD=3.3 & 5V 36 Frequency
35 37 Crosstalk vs .Frequency 38 Crosstalk vs .Frequency 39 Crosstalk vs .Frequency 40 Crosstalk vs .Frequency 41 Closed Loop Response 42 Closed Loop Response 43 Closed Loop Response 44 Closed Loop Response 45 Supply Current vs. Supply Voltage 46 Output Power vs. Supply Voltage 47 Output Power vs. Supply Voltage 48 Output Power vs. Load Resistance 49 Output Power vs. Load Resistance
VDD=5VA Po=1.5WA RL=4 ohmA BTLA Right to Left & Left to Right VDD=3.3VA Po=0.75WA RL=4 ohmA BTLA Right to Left & Left to Right VDD=5VA Po=75mWA RL=32 ohmA SEA Right to Left & Left to Right VDD=3.3VA Po=35mWA RL=32 ohmA SEA Right to Left & Left to Right VDD=5VA Av=-2V/VA Po=1.5WA BTLA Gain & Phase VDD=3.3VA Av= -2V/VA Po=0.75WA BTLA Gain &Phase VDD=5VA Av=-1V/VA Po=0.5WA SEA Gain &Phase VDD=3.3VA Av= -1V/VA Po=0.25WA SEA Gain &Phase Stereo BTL & Stereo SE THD+N=1%A BTLA Each ChannelA RL=3 & 4 & 8 ohm THD+N=1%A SEA Each ChannelA RL=3 & 4 & 8 ohm THD+N=1%A BTLA Each ChannelA VDD=3.3 & 5V THD+N=1%A SEA Each ChannelA VDD=3.3 & 5V
50 Power Dissipation vs. Output Power VDD=5VA BTLA Each ChannelA RL=3 & 4 & 8ohm 51 Power Dissipation vs. Output Power VDD=3.3VA BTLA Each ChannelA RL=3 & 4 & 8ohm 52 Power Dissipation vs. Output Power VDD=5VA SEA Each ChannelA RL=4 & 8 &32 ohm 53 Power Dissipation vs. Output Power VDD=3.3VA SEA Each ChannelA RL=4 & 8 &32 ohm
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Application Information
Gain Setting Resistors, RF and RI The gain for each audio input of the EUA5202 is set by resistors by resistors RF and RI according to equation 1 for BTL mode. Input Capacitor, CI In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and RI form a high-pass filter with the corner frequency determined in equation 4.
f c(highpass ) = 1 2 R C II
R F BTL Gain = -2 R I
-------------------------------- (1)
------------------- (4)
BTL mode operation brings about the factor 2 in the gain equation due to the inverting amplifier mirroring the voltage swing across the load. Given that the EUA5202 is a MOS amplifier, the input impedance is very high, value of RF increases. In addition, a certain range of RF values is required for proper start-up operation of the amplifier. Taken together it is recommended that the effective impedance seen by the inverting node of the amplifier be set between 5k and 20k .The effective impedance is calculated in equation 2.
RR EffectiveImpedance =
F FI I
R +R
-------------------- (2)
The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where RI is 10k and the specification calls for a flat bass response down to 40Hz. Equation 8 is reconfigured as equation 5.
1 C= I 2 R f IC
As an example consider an input resistance of 10k and a feedback resistor of 50k. The BTL gain of the amplifier would be -10 and the effective impedance at the inverting terminal would be 8.3k, which is well within the recommended range. For high performance applications metal film resistors are recommended because they tent to have lower noise levels than carbon resistors. For values of RF above 50k the amplifier tends to become unstable due to a pole formed from RF and the inherent input capacitance of the MOS input structure. For this reason, a small compensation capacitor of approximately 5pF should be places in parallel with RF when RF is greater than 50k. This, in effect, creates a low pass filter network with the cutoff frequency defined in equation 3.
1 f (lowpass) = c 2 R C FF
------------------------------------ (5)
-------------------- (3)
In this example, CI is 0.40 F so one would likely choose a value in the range of 0.47F to 1F. A further consideration for this capacitor is the leakage path from the input source through the input network (RI, CI) and the feedback resistor (RF) to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher that the source dc level. Please note that it is important to confirm the capacitor polarity in the application.
For example, if RF is 100k and CF is 5 pF then fC is 318 KHz, which is well outside of the audio range.
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Power Supply Decoupling, CS
The EUA5202 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent - series - resistance (ESR) ceramic capacitor, typically 0.1F placed as close as possible to the device VDD lead works best. For filtering lower - frequency noise signals, a larger aluminum electrolytic capacitor of 10 F or greater placed near the audio power amplifier is recommended. Bypass Capacitor, CB The bypass capacitor, CB, is the most critical capacitor and serves several important functions. During startup or recovery from shutdown mode, CB determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, CB, values of 0.1 F to 1 F ceramic of tantalum low-ESR capacitors are recommended for the best THD and noise performance. In Figure 2, the full feature configuration, two bypass capacitors are used. This provides the maximum separation between right and left drive circuits.When absolute minimum cost and/or component space is required, one bypass capacitor can be used as shown in Figure 1. It is critical that terminals 6 and 19 be tied together in this configuration. Output Coupling Capacitor, CC In the typical single-supply SE configuration, and output coupling capacitor (CC) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor and impedance of the load form a high-pass filter governed by equation 6
1
The main disadvantage, from a performance standpoint, is the load impedances are typically small, which drives the low-frequency corner higher degrading the bass response. Large values of CC are required to pass low frequencies into the load. Consider the example where a CC of 330 F is chosen and loads vary from 3, 4, 8, 32, 10k, to 47k. Table 1 summarizes the frequency response characteristics of each configuration.
Table1. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode
RL
CC
Lowest Frequency
3 4 8 32 10000 47000
330 F 330 F 330 F 330 F 330 F 330 F
161 Hz 120 Hz 60 Hz 15 Hz 0.05 Hz 0.01 Hz
As Table 1 indicates, most of the bass response is attenuated into 4- load, an 8- load is adequate, headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.
Using Low-ESR Capacitors Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. Bridged-tied Load Versus Single-ended Mode
fc(high)=
2 R C
L
---------------------------- (6)
C
Figure 56 show a linear audio power amplifier (APA) in a BTL configuration. The EUA 5202 BTL amplifier consists of two linear amplifiers driving both ends of the load. There are several potential benefits to this differential drive configuration, but initially consider power to the load. The differential drive to the speaker means that as one side is slewing up, the other side is slewing down, and vice versa. This in effect doubles the voltage swing on the load as compared to a ground referenced load. Plugging 2 x VO(PP) into the power equation, where voltage is squared, yields 4 x the output power from the same supply rail and load impedance (see equation 7 )
V(rms)x
V O(PP) 22
Power x
V (rms) R
L
2
------ (7)
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Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4 N the output power of the SE configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal considerations section. Single-Ended Operation In SE mode (see Figure56 and Figure57), the load is driven from the primary amplifier output for each channel (OUT+, terminals 22 and 3). In SE mode the gain is set by the RF and RI resistors and is shown in equation 9. Since the inverting amplifier is not used to mirror the voltage swing on the load, the factor of 2, from equation 5, is not included. In a typical computer sound channel operating at 5V, bridging raises the power into an 8- speaker from a singled -ended (SE, ground reference) limit of 250 mW to 1W. In sound power that is a 6-dB improvement-- which is loudness that can be heard. In addition to increased power there are frequency response concerns. Consider the single-supply SE configuration shown in Figure 57. A coupling capacitor is required to block the dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33F to 1000F) so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting low-frequency performance of the system. This frequency limiting effect is due to the high pass filter network created with the speaker impedance and the coupling capacitance and is calculated with equation 8.
R SE Gain = - F -------------------------------------- (9) R I The output coupling capacitor required in single-supply SE mode also places additional constraints on the selection of other components in the amplifier circuit. The rules described earlier still hold with the addition of the following relationship (see equation 10):
1 1 < 1 RC LC
C x 25 k B
C R I I
--------------- (10)
fC=
1 2 R LCC
------------------------------------ (8)
For example, a 68F capacitor with an 8- speaker would attenuate low frequencies below 293 Hz. The BTL configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency performance is then limited only by the input network and speaker response. Cost and PCB space are also minimized by eliminating the bulky coupling capacitor.
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Input MUX operation
Working in concert with the SE/ BTL feature, the HP/LINE MUX feature gives the audio designer the flexibility of a multichip design in a single IC (see Figure 58). The primary function of the MUX is to allow different gain settings for BTL versus SE mode. Speakers typically require approximately a factor of 10 more gain for similar volume listening levels as compared to headphones. To achieve headphone and speaker listening parity, the resistor values would need to be set as follows:
SE Gain R F(HP) = - (HP) R I (HP)
-------------------------- (11)
If, for example RI (HP) = 10 k and RF (HP) = 10k then SE Gain (HP) = -1 R F (LINE) -------------------- (12) BTL Gain = -2 R (LINE) I (LINE) If, for example RI (LINE) = 10k and RF (LINE) = 50k then BTL Gain (LINE) = -10
SE/BTL Operation The ability of the EUA5202 to easily switch between BTL and SE modes is one of its most important cost saving features. This feature eliminates the requirement for an additional headphone amplifier in applications where internal stereo speakers are driven in BTL mode but external headphone or speakers must be accommodated. Internal to the EUA5202, two separate amplifiers drive LOUT- and ROUT- (terminals 10 and 15).When SE/ BTL is held high, the OUT- amplifier are in high output impedance state, which configures the EUA5202 as an SE driver from LOUT + and ROUT + (terminal 3 and 22). IDD is reduced by approximately one-half in SE mode. Control of the SE/ BTL input can be from a logic-level CMOS source, or, more typically, from a resistor divider network as shown in Figure 59.
Using a readily available 1/8-in. (3.5mm) stereo headphone jack, the control switch is closed when no plug is inserted. When closed the 100-k/1-k divider pulls the SE/ BTL input low. When a plug is inserted, the OUT- amplifier is shutdown causing the speaker to mute (virtually open-circuits the speaker). The OUT+ amplifier then drives through the output capacitor (CO) into the headphone jack. As shown n the full feature application (Figure 2), the input MUX control can be tied to the SE/ BTL input. The benefits of doing this are described in the following input MUX operation section. Another advantage of using the MUX feature is setting the gain of the headphone channel to -1. This provides the optimum distortion performance into the headphones where clear sound is more important. Refer to the SE/ BTL operation section for a description of the headphone hack control circuit.
Mute and Shutdown Mode The EUA5202 employs both a mute and a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held low during normal operation when the amplifier is in use. Pulling SHUTDOWN high causes the outputs to mute and the amplifier to enter a low-current state, IDD = 5 A. SHUTDOWN or MUTE IN should never be left unconnected because amplifier operation would be unpredictable. Mute mode alone reduces IDD to 1.5 mA.
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Package Information
Use as much copper area as possible
Bottom view
Exposed Pad
NOTE 1. Package body sizes exclude mold flash protrusions or gate burrs 2. Tolerance 0.1mm unless otherwise specified 3. Coplanarity :0.1mm 4. Controlling dimension is millimeter. Converted inch dimensions are not necessarily exact. 5. Die pad exposure size is according to lead frame design. 6. Standard Solder Map dimension is millimeter. 7. Followed from JEDEC MO-153
SYMBOLS A A1 A2 b C D E E1 e L y DIMENSIONS IN MILLIMETERS MIN. NOM. MAX. ----------1.15 0.00 -----0.10 0.80 1.00 1.05 0.19 -----0.30 0.09 -----0.20 7.70 7.80 7.90 -----6.40 ----4.30 4.40 4.50 -----0.65 ----0.45 0.60 0.75 ----------0.10 0 -----8 DIMENSIONS IN INCHES MIN. NOM. MAX. ----------0.045 0.000 -----0.004 0.031 0.039 0.041 0.007 -----0.012 0.004 -----0.008 0.303 0.307 0.311 -----0.252 -----0.169 0.173 0.177 -----0.026 -----0.018 0.024 0.030 ----------0.004 0 -----8
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